• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
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    • 专利摘要:
    The invention relates to a bandpass filter for a frequency-tunable microwave frequency, comprising at least one resonator ®, each resonator comprising a cavity (30) having a substantially cylindrical conducting wall (50) along an axis Z, and to least one dielectric element disposed inside the cavity, -said resonator resonant on two perpendicular polarizations respectively having distributions of the electromagnetic field in the cavity being deduced from each other by a rotation of 90 ° and according to the same frequency, -the wall of the cavity (50) comprising an insert section (20) opposite said element having a shape different from a non-facing section of the element, -the insert section (20) and the element being able to rotate relative to each other along the axis Z so as to define at least a first (P1) and a second relative positions differing from an angle e substantially equal to 45 ° to 20 °.
    公开号:FR3015783A1
    申请号:FR1303030
    申请日:2013-12-20
    公开日:2015-06-26
    发明作者:Hussein Ezzeddine；Aurelien Perigaud；Olivier Tantot；Nicolas Delhote；Stephane Bila；Serge Verdeyme；Damien Pacaud；Laetitia Estagerie
    申请人:Centre National dEtudes Spatiales CNES；Centre National de la Recherche Scientifique CNRS；Thales SA；
    IPC主号:
    专利说明:

    [0001] FIELD OF THE INVENTION The present invention relates to the field of frequency filters in the field of microwave waves, typically of frequencies between 1 GHz at 30GHz. More particularly, the present invention relates to frequency tunable band pass filters. STATE OF THE ART The treatment of a microwave wave, for example received by a satellite, requires the development of specific components, allowing the propagation, amplification, and filtering of this wave. For example, a microwave received by a satellite must be amplified before being sent back to the ground. This amplification is only possible by separating all the frequencies received into channels, each corresponding to a given frequency band. The amplification is then carried out channel by channel. Channel separation requires the development of bandpass filters. The development of the satellites and the increased complexity of the signal processing to be performed, for example reconfiguration of the in-flight channels, has led to the need to implement frequency-tunable band pass filters, i.e. which it is possible to adjust the central filtering frequency commonly referred to as tuning frequency 25 of the filter. One of the known technologies of tunable bandpass filters in the microwave domain is the use of passive semiconductor components, such as PIN diodes, continuously variable capacitors, or capacitive switches. Another technology is the use of MEMS (for micro electromechanical systems) of the ohmic or capacitive type.
    [0002] These technologies are complex, power-consuming and unreliable. These solutions are also limited in the amount of signal power processed. In addition, the frequency tunability results in a significant degradation of the filter performance, such as its Q quality factor. Finally, the RF losses (realized band, "Return Loss", insertion losses, etc.) are degraded. by the change of frequency. In addition, the technology of the filters based on dielectric elements is known. It allows non-tunable band pass filters.
    [0003] These filters typically comprise an at least partially closed cavity, comprising a conducting wall (typically metallic, for example aluminum or invar) in which is disposed a dielectric element, typically of round or square shape (the dielectric material is typically zirconia, alumina or BMT).
    [0004] An input excitation means introduces the wave into the cavity (for example a coaxial cable terminated by an electric probe or an iris-coupled waveguide) and an output excitation means of the same nature bring the wave out of the cavity. A bandpass filter allows the propagation of a wave over a certain frequency range and attenuates this wave for the other frequencies. This defines a bandwidth and a central frequency of the filter. For frequencies around its center frequency, a bandpass filter has high transmission and low reflection. The filter bandwidth is characterized in different ways depending on the nature of the filter. Parameter S is a parameter that accounts for filter performance in terms of reflection and transmission. S11, or S22, corresponds to a measurement of the reflection and S12, or S21, to a measurement of the transmission. A filter performs a filtering function. This function can generally be approximated via mathematical models (functions of Chebychev, Bessel, etc.). These functions are usually based on polynomial relationships. For a filter performing a generalized Chebychev or Chebychev type filtering function, the filter bandwidth is determined at the S11 (or S22) equilibrium, for example at 15 dB or 20 dB of reduction of the reflection with respect to its off-level. bandaged. For a filter performing a Bessel type function, the band is taken at -3dB (when S21 crosses S11 if the filter has negligible losses).
    [0005] A filter typically comprises at least one resonator comprising the metal cavity and the dielectric element. A resonance mode of the filter corresponds to a particular distribution of the electromagnetic field which is excited at a particular frequency. In order to increase their selectivity, i.e. their ability to attenuate the signal out of the bandwidth, these filters may be composed of a plurality of resonators coupled together. The center frequency and the passband of the filter depend both on the geometry of the cavities and the dielectric elements, as well as the coupling of the resonators with each other as well as couplings to the input and output excitation means of the filter. Coupling means are for example openings or slots called iris, electrical or magnetic probes or microwave lines. The filter passes a signal whose frequency is in the bandwidth, but the signal is nevertheless attenuated by the losses of the filter. The tuning of the filter making it possible to obtain a transmission maximum for a given frequency band is very difficult to carry out and depends on all the parameters of the filter. It is moreover dependent on the temperature. In order to adjust the filter to obtain a precise center frequency of the filter, the resonant frequencies of the filter resonators can be very slightly modified by means of metal screws, but this method is empirically done, is very expensive. in time and allows only a very low frequency tunability, typically of the order of a few%. In this case, the objective is not the tunability but the obtaining of a precise value of the central frequency, and it is desired to obtain a reduced sensitivity of the frequency of each resonator with respect to the depth of the screw. The circular or square symmetry of the resonators simplifies the design of the filter.
    [0006] In general, a resonator has, according to its geometry, one or more resonance modes, each characterized by a particular (remarkable) distribution of the electromagnetic field causing a resonance of the microwave wave in the structure at a partocular frequency. For example, resonance modes TE (for Electric Transverse or H in English terminology) or TM (for Magnetic Transverse or E in English terminology) having a certain number of energy maxima identified by indices, can be excited in the resonator at different frequencies. FIG. 1 describes, by way of example, the resonance frequencies of the different modes for an empty circular cavity as a function of the dimensions of the cavity (diameter D and height H). To optimize the compactness of the filters, resonator filters operating in several modes (typically 2 or 3) are known in the art. In particular, filters operating in a dual mode ("dual mode filter" in English terminology) are known. These modes have two perpendicular polarizations X and Y having a remarkable and specific distribution of the electromagnetic field in the cavity: the distributions of the electromagnetic fields corresponding to the two polarizations are orthogonal and are deduced from each other by a rotation of 90 ° around an axis of symmetry of the resonator. If the symmetry of the resonator is perfect, the two orthogonal polarizations have the same resonance frequency and are not coupled. The coupling between polarizations is obtained by breaking the symmetry, for example by introducing a discontinuity (perturbation) at 45 ° of the X and Y polarization axes, typically using metal screws. In addition, the resonant frequencies can be tuned (possibly at different frequencies) by introducing discontinuities (disturbances) in the polarization axes (X and Y). Thus the two polarizations X and Y of a dual mode can resonate at the same frequency (symmetry along the axes of polarization) or two slightly different frequency (asymmetry along the axes of polarization). 3015 783 5 The dual modes thus make it possible to make two electrical resonances in a single resonant element. Several modes having these particular field distributions can be used. For example the dual modes TE1 1n (M'in) are widely used in cavity filters because they result in a good compromise between a high quality factor (especially since the index n is large), a reduced space requirement (divided by 2 by using dual modes) and high frequency isolation compared to other resonance modes (which we do not want to couple to ensure the proper operation of the filter). OBJECT OF THE INVENTION The object of the present invention is to provide cavity filters with compact, center-frequency tunable dielectric elements and not having the aforementioned drawbacks (quality factor and RF losses degraded by tunability , poor power handling ...). DESCRIPTION OF THE INVENTION To this end, the subject of the invention is a bandpass filter for a frequency-tunable microwave wave, comprising at least one resonator, each resonator comprising a cavity having a substantially cylindrical conducting wall along an axis. Z, and at least one dielectric element disposed inside the cavity, the resonator resonating on two perpendicular polarizations respectively having distributions of the electromagnetic field in the cavity being deduced from each other by a rotation of 90 °, -the wall of the cavity comprising an insert section facing the element 30 having a shape different from a non-facing section of the element, -the insert section and the element being suitable to rotate relative to each other along the axis Z so as to define at least first and second relative positions differing from an angle substantially equal to 45 ° to 20 °.
    [0007] According to one embodiment, at least one of the shape of the insert section and the shape of the element comprises at least two orthogonal planes of symmetry intersecting along the axis Z. Advantageously, the shape of the section of the The insert and the shape of the element 5 each comprise at least two orthogonal planes of symmetry S1, S3, Si1, Si3 intersecting along the axis Z. Advantageously, the first position is such that the plane of symmetry of the section d insert coincide with the plane of symmetry of the element to 10 °. According to one embodiment at least one of the shape of the insert section and the shape of the element has four symmetry planes S1, S2, S3, S4, Si1, Si2, Si3, Si4, two planes of consecutive symmetry being separated by an angle of 45 °, and intersecting along the axis Z. Advantageously, at least one of the shape of the insert section 15 and the shape of the element has concavities and / or convexities whose extrema are located in the vicinity of axes of symmetries. Preferably, the substantially cylindrical shape has a guide curve chosen from a circle, a square. Preferentially; a resonant mode of the resonator is of the type H113 having three maximas of the electric field in said cavity along the axis Z. In a variant, the resonator further comprises rotation means capable of performing said rotation. In one embodiment, the insert section is movable relative to the conductive wall. Preferably, the movable insert section comprises a movable adjustment ring. According to one embodiment, the dielectric element is movable relative to the conductive wall. Advantageously, the rotation means comprise a rod integral with the dielectric element and comprising a dielectric material. According to one embodiment, the filter comprises a plurality of resonators and coupling means adapted to couple together two consecutive resonators.
    [0008] Preferably, the filter further comprises connecting means adapted to equalize the respective rotations of the rotation means of the resonators. Advantageously, the connecting means comprise said rod integral with a plurality of elements arranged along the rod. According to another aspect, the invention relates to a microwave circuit comprising at least one filter according to the invention. Other features, objects and advantages of the present invention will appear on reading the detailed description which follows and with reference to the appended drawings given by way of non-limiting examples and in which: FIG. 1 illustrates the resonance modes of FIG. an empty circular cavity. - Figure 2 describes a filter according to a variant of the invention in a cross section. - Figure 3 describes a filter according to another embodiment of the invention in a cross section. FIG. 4 describes a filter according to a preferred variant of the invention comprising at least four orthogonal planes of symmetry. FIG. 4a describes the resonator of the filter in a first position P1 and FIG. 4b describes the resonator of the filter in a second relative position P2. - Figure 5 describes the filter of Figure 4 seen in perspective. FIG. 5a describes the resonator of the filter in a first position P1 and FIG. 5b describes the resonator of the filter in a second relative position P2. FIG. 6 illustrates an alternative form of insert section and element according to the invention (position P1, position 6b P2); FIG. 7 illustrates another variant of insert section and element section the invention (7a position P1, 7b position P2) - Figure 8 illustrates another alternative form of insert section and element according to the invention (8a position P1, 8b position P2) - Figure 9 illustrates the variations of the electric field of a resonant polarization in the cavity of the filter resonator according to the invention. FIG. 10 illustrates a filter comprising two resonators each comprising a cavity and a dielectric element, the resonators being coupled together by means of a coupling means (FIG. 10a position P1, FIG. 10b, position P2). - Figure 11 illustrates a filter according to the invention having input and output means performing a lateral coupling. Figure 12 illustrates a filter comprising three resonators (OK ). FIG. 13 illustrates the frequency behavior of the filter of FIG. 10. FIG. 14 describes a second variant of the invention according to which the element is movable with respect to the conducting wall. DETAILED DESCRIPTION OF THE INVENTION The invention consists in producing a tunable band pass filter in central frequency of "dual mode" type from a rotation of different elements composing the filter. The filter comprises at least one resonator R, each resonator comprising a cavity 30 having a conductive wall, typically metallic, substantially cylindrical along an axis Z, and at least one dielectric element disposed inside the cavity, FIG. 2, describes a cross section of a resonator R of the filter according to the invention in a plane perpendicular to the Z axis. The filter operates in a dual mode ("dual mode filter"), which means that the resonator resonates on two perpendicular polarizations called X and Y which respectively have distributions of the electromagnetic field in the cavity 30 being deduced from each other by a rotation of 90 °. Both polarizations may resonate at the same frequency or at slightly different frequencies. In the latter case the frequency response of the filter is asymmetrical.
    [0009] In addition, the symmetry of the mode can be slightly broken to couple the two polarizations (see below).
    [0010] In the cavity 30 is disposed at least one dielectric element 21. The wall of the cavity is generally cylindrical but comprises a specific section, called insert section 20, located opposite the element 21, that is to say corresponding to the portion of the wall substantially "fa ce" to the element in the cavity 30. The insert section 20 has a shape 10 different from the shape of a section of the same wall not located opposite the 'element. Preferably, it is the shape of the inner wall of the cavity that has a specific shape. For example in Figures 2a and 2b, the wall of the cavity has a cylindrical shape of revolution, but the shape of the insert section 10 differs from the circle. The insert section 20 and the element 21 are able to rotate relative to each other along the axis Z so as to define at least a first relative position P1 and a second relative position P2 differing from one another. an angle substantially equal to 45 ° to 20 °. FIG. 2a describes the resonator according to the first position P1 and FIG. 2b describes the resonator according to the second relative position P2. The relative angle between the element and the insert section varies from about 45 ° + 1-20 ° between the two positions. Thus the relative angle is between 25 ° and 65 °. Preferably, the relative angle is between 45 ° + 1-10 °, ie between 35 ° and 55 °. The contours of the insert section and the element are adapted so that the first position P1 corresponds to a resonator geometry resonating at a first central frequency f1, and the second position P2 corresponds to a resonator geometry resonating according to a second Center frequency f2. Thus, the relative rotation of the element relative to the insert section makes it possible to modify the central frequency of the filter according to the invention, according to at least two central frequency fletches f2, which is suitable for applications of the type " channel jump. Such an effect is achieved by varying the rotational capacitive effect as will be described later. A filter according to the invention thus has many advantages. The filter is both dual, with all the associated benefits such as compactness, and tunable. The RF performance is not substantially degraded by the frequency change, and the quality factor Q is not significantly degraded compared with those conventionally obtained with resonant cavities, among others because of the limited impact of dielectric element 21 on the losses of the filter. Typically a factor Q> 10000 is obtained for a filter according to the invention, whereas the other known tuning solutions, either are not applicable to the production of a dual mode filter, or strongly degrade the losses compared to a filter without a tuning element. In addition, it has a narrow band (see below for an example of performance as a function of frequency). In addition, the filter is capable of supporting a high power microwave signal, typically greater than 150W. These levels of power withstand are totally unimaginable with semiconductor components or MEMS. According to one embodiment, when only one of the two forms has two planes of orthogonal symmetries, the shape with these planes is fixed.
    [0011] Preferably, the resonator of the filter according to the invention further comprises rotation means adapted to perform the rotation. Preferably, a filter according to the invention has an insert section or an element having properties of particular symmetry allowing the filter to optimally fulfill the desired function. Thus at least one of the shape of the insert section 20 and the shape of the element 21 comprises at least two orthogonal planes of symmetry intersecting along the Z axis. In FIG. for example, it is the shape 11 of the element 21, that is to say the outer contour of the element in a section perpendicular to the axis Z, which comprises at least two orthogonal planes of symmetry Si1 and Si3, intersecting along the Z axis, schematized along two lines in solid lines in the sectional diagrams of Figures 2a and 2b. The angle of rotation can be referenced, for example, with respect to the axes S1 and S1, but it is the relative angle between the element and the insert section which varies by approximately 45 ° +/- 20 ° between both positions. FIG. 3 (FIGS. 3a and 3b) illustrates another geometry variant of the shape of the insert section 20 and the shape of the element 21. FIG. 3a describes the resonator according to the first position P1 and FIG. FIG. 3b describes the resonator according to the second relative position P2. In FIG. 3, the shape of the insert section 20, that is to say the perimeter of the wall in a section opposite the element (preferably the internal perimeter), comprises at least two orthogonal planes of symmetry S1 and S3 intersecting along the Z axis, schematized along two dotted lines in the sectional diagrams of Figures 3a and 3b. The shape of the insert section 10 is understood to be the overall shape, leaving out fine adjustment elements, such as 45 ° screws (not shown), locally introducing a slight asymmetry to couple the two polarizations to one another. In this example, the form 21 of the element 11 also has two planes of symmetries Si1 and Si3. Thus according to this variant the form 10 of the insert section 20 and the shape 11 of the element 21 each comprise at least two orthogonal planes of symmetry, respectively (51, S3) and (Si1, Si3), intersecting each other. the Z axis. According to a preferred variant, for an easier optimization of the different elements of the filter, the first position P1 is such that the symmetry planes S1 and S3 of the insert section coincide with the planes of symmetry Si Si3 of the element 21 to 10 °, as shown in FIG. 3. According to a preferred variant, illustrated in FIGS. 4 and 5, the shape of the insert section and / or the shape of the element has four symmetry planes designated Sl, S2, S3 and S4 for the insert section and Si1, Si2, Si3 and Si4 for the element, two consecutive planes of symmetry being separated by an angle of 45 °, and intersecting at Z axis. This geometry also allows an optimization calculation of the dual mode filter. us faster and simpler, with a simplified design of the filter structure. As illustrated in FIG. 4, for the variant according to which for the position P1 the planes of symmetry coincide, during a rotation of 45 ° for the position P2, there is always coincidence since the consecutive planes are separated by one angle of 45 °. For example according to P1: S1 = Sil; S2 = Si2; S3 = Si3; S4 = Si4. According to P2, for a rotation of 45 ° of the insert section, or planes 51 to S4. Sl = Si2; S2 = Si3; S3 = Si4; S4 = Sil.
    [0012] FIG. 4 is a sectional view perpendicular to the Z axis, and FIG. 5 is a perspective view, for viewing the insert section 20. FIGS. 4a and 5a describe the resonator R according to the first position P1 and FIGS. Figures 4a and 4b describe the resonator R according to the second relative position P2. FIGS. 4 and 5 also illustrate a first variant in which it is the insert section 20 which is movable with respect to the element 21. Preferably, the insert section is also movable relative to the conductive wall 50 of the resonator. R, in order to maintain the continuity of the wall 50. A rotating movable insert section is then disposed inside the cavity 30. The shape of the insert section is obtained by adding metal parts 51 (which are for example convexities by considering these surfaces from inside the cavity), along the section, these locally modifying parts, here decreasing locally, in the regions facing the element, the diameter of the cavity and therefore the distance between the element and the metal wall 50. For example the insert section corresponds to a setting ring made mobile. According to the azimuthal angle, the radius of the ring is variable so the perturbation seen by the two polarizations X and Y is different in the positions P1 and P2 (see below). For example, the adjusting ring is made mobile by means of a rotary joint in order to maintain the electrical continuity between the fixed part and the mobile part.
    [0013] In Figure 5 in perspective, the structure of the element and the insert section in the Z direction is homogeneous. This homogeneity corresponds to a preferred embodiment because it is simpler to carry out, but the Z structure could also be variable. A cylindrical surface is defined by a guide curve described by a straight line referred to as the generatrix of the cylinder. The guide curve of the filter wall according to the invention is preferably a circle or a square, for reasons of intrinsic symmetry of this type of cavity and ease of design and manufacture.
    [0014] A dual mode is established preferentially according to certain particular modes of cavity, thus corresponding to preferred embodiments of the invention. An example is the type of mode TE11 n (or Hl 1 n in English terminology), n corresponding to the number of variations of the electric field (minimum or maximum) along the Z axis of the cavity. According to a preferred embodiment, n = 3, this case corresponding to a compromise between size and electrical performance (losses and frequency insulation). Figures 6, 7 and 8 illustrate alternative forms of insert section 10 and element 11 and relative rotation of one with respect to the other of a resonator according to the invention. In Figure 8 concavities 80 (views of the interior of the cavity) locally increase the distance between the element and the metal wall. To respect the conditions of symmetry while obtaining a variation of the capacitive effect, according to one embodiment the shape of the insert section and / or the shape of the element has concavities and / or convexities whose extrema are located in the vicinity of axes of symmetry of the resonator. For the insert section: in the vicinity of the planes of symmetry (S1, S2, S3, S4). For the element: in the vicinity of the planes of symmetry (Sil, Si2, Si3, Si4). This embodiment is of course compatible with a system comprising only two planes of symmetry, as illustrated in FIGS. 2 and 3. In addition, it is of course not necessary for concavity / convexity to exist in the vicinity of each axis. of symmetry, the constraint being to respect the condition of symmetry.
    [0015] FIG. 9 illustrates the variations of the electric field of one of the resonant (X or Y) polarizations in the cavity of the resonator of FIGS. 4-5. FIG. 9a describes the resonator R according to the first relative position P1 and FIG. 9b describes the resonator R according to the second relative position P2, for which the insert section 20 has rotated 45 ° with respect to the element 21. .
    [0016] The dashed areas referenced 90 illustrate the areas for which the electric field has a maximum. For the first position P1, the electric field is concentrated between the points of the element and the convexities / excrescences 51 of the insert section. For the second position P2 this electric field is concentrated between the edges of the element and the convexities 51. The modification of the resonant frequency of the filter is obtained by varying the capacitive effect between the insert 21 and the cross section. In fact, it is possible to model the frequency behavior of a resonator by an equivalent electrical circuit: a parallel association between resistance and capacitance (resonator RLC). This circuit has a resonance frequency function of the product L.C. When playing on the capacitive effect, the value of the capacitance varies, resulting in a variation of the resonance frequency. The capacitive effect induced by the presence of a dielectric element is a function of its geometry and the characteristics of the material which composes it (dielectric permittivity), but also of the resonance mode (in particular of the associated distribution of the electromagnetic field). Depending on the mode (or polarization for a dual mode), the electromagnetic field 20 is only influenced by a part of the element. A variation of the shape of the element in areas of high amplitude of the electric field changes the capacitive effect of the resonator. The contrast obtained on the capacitive effect is maximized when this variation is localized on a maximum of electric field. In the case of a dual mode filter, the effect must be the same on every polarization to obtain the same frequency shift for both polarizations. Alternatively, the filter comprises a plurality of resonators and coupling means adapted to couple together two consecutive resonators. FIG. 10 (FIG. 10a position P1, FIG. 10b, position P2) illustrates a filter 100 comprising two resonators R1 and R2 each comprising a cavity 102 and 103, and a dielectric element 106, 107, the resonators being coupled to one another using a coupling means 101, here an iris. Input and output means 105 respectively allow the microwave wave to enter and exit the filter respectively. The cylindrical metal wall 50 is in this example common to both cavities, and the coupling is made by the bottom. But the filter according to the invention 5 is of course compatible with a lateral coupling, as shown in FIG. 11 The filter 100 of FIG. 10 comprises two cavities, each resonating on two polarizations, and thus constitutes a so-called "4-pole" filter. The invention is of course compatible with 3 cavities (or more), making it possible to obtain a narrower bandwidth, as illustrated in FIG. 12. An example of the frequency behavior of the filter of FIG. 10 is illustrated in FIG. 13a position P1, figure 13b position P2). The dual mode is of type H113 and the filter parameters of this example are: Total length: 90 mm; diameter of the cylinder 27 mm; use of a movable adjusting ring; Alumina dielectric element (permittivity 9.4) square-shaped 12 mm x 12 mm side and Z-thickness of 4 mm. The curves 111 and 112 (solid line) correspond to the curves of the S11 type (filter reflection) and the curves 113 and 114 (dotted line) to the S21 type curves (transmission of the filter). Between the two positions P1 and P2 there is a variation of about 150 MHz (1.5%) in the resonant frequency. According to a second variant of the invention illustrated in FIG. 14 (FIG. 14a position P1, FIG. 14b, position P2) the element is movable with respect to the conducting wall and relative to the insert section which is fixed. In this example, the rotation means comprise a rod 120 made of dielectric material integral with the element, or a plurality of elements when the structure of the cavities allows it, as in FIG. 12. Indeed in FIG. 12 the coupling is made by the bottom, the successive elements are thus aligned along the same axis and can therefore all be integral with the same rod. This geometry has the advantage of allowing control of all the rotations of the plurality of elements with the same element. This geometry is of course compatible with a lateral coupling, rather than the bottom as illustrated in Figure 14.
    [0017] In one embodiment, the filter further comprises connecting means adapted to equalize the respective rotations of the rotation means of the resonators.
    [0018] For the second variant in which the elements are movable and integral with the same rod 120, the rod is also a connecting means. The rotation means may also comprise a stepping motor for controlling the rotation of the elements, in the case where a reconfiguration of the filter must be carried out in flight for example.
    [0019] According to another aspect the invention also relates to a microwave circuit comprising at least one filter according to the invention.
    权利要求:
    Claims (17)
    [0001]
    REVENDICATIONS1. A bandpass filter (100) for a frequency-tunable microwave, comprising at least one resonator (R, R1, R2), each resonator comprising a cavity (30, 102, 103) having a substantially cylindrical conductive wall (50) along an axis Z, and at least one dielectric element (21, 106, 107) disposed inside the cavity, said resonator resonating on two perpendicular polarizations (X, Y) respectively having distributions of the electromagnetic field in the cavity being deduced one of the other by a rotation of 90 °, 10 -the wall of the cavity (50) comprising an insert section (20) facing said element (21, 106, 107) having a shape (10) different from a section not located opposite the element, the insert section (20) and the element (21, 106, 107) being able to rotate relative to one another according to the Z axis so as to define at least a first (P1) and a second (P2) po relative positions differing by an angle substantially equal to 45 ° to 20 °.
    [0002]
    2. The filter of claim 1 wherein at least one of the shape (10) of the insert section (20) and the shape (11) of the element (21) comprises at least two orthogonal planes of symmetry. (SI, S3), (Si1, Si3) intersecting along the Z axis.
    [0003]
    3. Filter according to one of claims 1 or 2 wherein the form (10) of the insert section (20) and the shape (11) of the element (21) each comprise at least two orthogonal planes of symmetry (S1, S3), (Si1, Si3) intersecting along the Z axis.
    [0004]
    4. The filter of claim 3 wherein the first position (P1) is such that said planes of symmetry (S1, S3) of the insert section (20) coincide with said symmetry planes (Si1, Si3) of the element to 10 °.
    [0005]
    5. Filter according to one of the preceding claims wherein at least one of the shape of the insert section (10) and the shape of the element (11) has four planes of symmetry (S1, S2, S3, S4), (Si1, Si2, Si3, Si4), two consecutive planes of symmetry being separated by an angle of 45 °, and intersecting along the Z axis.
    [0006]
    6. Filter according to one of claims 2 to 5 wherein at least one of the shape of the insert section (10) and the shape of the element (11) has concavities and / or convexities ( 51, 80) whose extrema are located in the vicinity of symmetry axes (S1, S2, S3, S4), (Si1, Si2, Si3, Si4).
    [0007]
    7. Filter according to one of the preceding claims wherein the substantially cylindrical shape 10 has a guide curve selected from a circle, a square.
    [0008]
    8. Filter according to one of the preceding claims wherein a resonator mode of the resonator is of the type H113 having three maximas of the electric field in said cavity along the Z axis.
    [0009]
    9. Filters according to one of the preceding claims wherein the resonator further comprises rotation means adapted to perform said rotation. 20
    [0010]
    10. Filter according to one of the preceding claims wherein the insert section is movable relative to the conductive wall.
    [0011]
    The filter of claim 10 wherein the movable insert section comprises a movable adjusting ring.
    [0012]
    12. Filter according to one of claims 1 to 9 wherein the dielectric element is movable relative to the conductive wall. 30
    [0013]
    13. The filter of claim 9 wherein said rotation means comprises a rod (120) integral with the dielectric element and comprising a dielectric material.
    [0014]
    14. Filter according to one of the preceding claims comprising a plurality of resonators (R1, R2) and coupling means (101) adapted to couple together two consecutive resonators.
    [0015]
    15. The filter of claim 14 further comprising connecting means adapted to equalize the respective rotations of the means of rotation of the resonators.
    [0016]
    16. The filter of claim 15 wherein the connecting means 10 comprise said rod secured to a plurality of elements arranged along the rod.
    [0017]
    17. Microwave circuit comprising at least one filter according to one of the preceding claims. 15
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    EP0757403A1|1997-02-05|Magnetic coupling device between a main conductor of a TEM line and a waveguide, forming a gamma/g/2 resonator
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    FR2675638A1|1992-10-23|Dielectric resonator device
    CA2753795C|2017-12-19|Microwave filter with a dielectric resonator
    EP0053986A2|1982-06-16|Bandpass filter tunable to a predetermined number of discrete frequencies in a broad frequency band
    FR2616972A1|1988-12-23|Frequency-tunable band-pass filter with yttrium iron garnet bead with wide tuning band
    EP0452211A1|1991-10-16|High frequency filter arrangement comprising at least one filter with variable frequency
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    同族专利:
    公开号 | 公开日
    ES2599803T3|2017-02-03|
    CA2875004A1|2015-06-20|
    US20150180106A1|2015-06-25|
    US9620837B2|2017-04-11|
    EP2887450A1|2015-06-24|
    EP2887450B1|2016-07-27|
    FR3015783B1|2016-01-15|
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    US5796318A|1994-01-24|1998-08-18|Murata Manufacturing Co., Ltd.|Dual TM-mode dielectric resonator apparatus equipped with window for electromagnetic field coupling, and band-pass filter apparatus equipped with the dielectric resonator apparatus|
    US20070159275A1|2006-01-12|2007-07-12|M/A-Com, Inc.|Elliptical dielectric resonators and circuits with such dielectric resonators|
    FI88228C|1991-05-09|1993-04-13|Telenokia Oy|Dielectric resonator construction|
    US5495216A|1994-04-14|1996-02-27|Allen Telecom Group, Inc.|Apparatus for providing desired coupling in dual-mode dielectric resonator filters|
    FR2803693B1|2000-01-12|2003-06-20|Cit Alcatel|RESONATOR, PARTICULARLY FOR THREE-FREQUENCY WIRE, AND FILTER COMPRISING SAME|
    FR3005209B1|2013-04-26|2015-04-10|Thales Sa|HYPERFREQUENCY FILTER WITH DIELECTRIC ELEMENT|DE102015012401A1|2015-09-24|2017-03-30|Airbus Ds Gmbh|Polarization-preserving filter for a dual polarized waveguide|
    US20180123255A1|2016-10-31|2018-05-03|Nokia Solutions And Networks Oy|Polarized Filtenna, such as a Dual Polarized Filtenna, and Arrays and Apparatus Using Same|
    EP3583655A1|2017-02-15|2019-12-25|Isotek Microwave Limited|A microwave resonator|
    GB2573381A|2018-03-16|2019-11-06|Isotek Microwave Ltd|A microwave resonator, a microwave filter and a microwave multiplexer|
    CN108461879B|2018-03-22|2020-09-01|京信通信技术有限公司|Cavity filter|
    CN112234328B|2020-10-10|2022-02-01|南宁国人射频通信有限公司|Medium dual-mode filter|
    法律状态:
    2015-11-23| PLFP| Fee payment|Year of fee payment: 3 |
    2016-11-28| PLFP| Fee payment|Year of fee payment: 4 |
    2017-11-27| PLFP| Fee payment|Year of fee payment: 5 |
    2018-11-27| PLFP| Fee payment|Year of fee payment: 6 |
    2020-10-16| ST| Notification of lapse|Effective date: 20200905 |
    优先权:
    申请号 | 申请日 | 专利标题
    FR1303030A|FR3015783B1|2013-12-20|2013-12-20|HYPERFREQUENCY FILTER BAND TUNABLE BY RELATIVE ROTATION OF AN INSERT SECTION AND A DIELECTRIC ELEMENT|FR1303030A| FR3015783B1|2013-12-20|2013-12-20|HYPERFREQUENCY FILTER BAND TUNABLE BY RELATIVE ROTATION OF AN INSERT SECTION AND A DIELECTRIC ELEMENT|
    EP14198053.2A| EP2887450B1|2013-12-20|2014-12-15|Tunable microwave bandpass filter by relative rotation of an insert section and a dielectric element|
    ES14198053.2T| ES2599803T3|2013-12-20|2014-12-15|Hyperfrequency filter passes tunable band by relative rotation of an insert section and a dielectric element|
    US14/574,255| US9620837B2|2013-12-20|2014-12-17|Bandpass microwave filter tunable by relative rotation of an insert section and of a dielectric element|
    CA2875004A| CA2875004A1|2013-12-20|2014-12-17|Bandpass microwave filter tunable by relative rotation of an insert section and of a dielectric element|
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